Simultaneous bidirectional serial link interface with optimized hybrid circuit

ABSTRACT

An integrated circuit (IC) chip includes transceiver circuitry. The transceiver circuitry includes a differential transmit circuit and a hybrid circuit. The differential transmit circuit includes a first transmit path for transmitting first data of a first polarity to a transmission line. A second transmit path generates replica first data having a second polarity opposite the first polarity. The hybrid circuit includes a first input path coupled to the second transmit path. A second input path is coupled to the transmission line for receiving a first summed signal including the first data and second data. The second data is received from the transmission line simultaneous with transmission of the first data along the transmission line. An output circuit generates an output representing a summation of the replica first data and the first summed signal.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a Continuation of U.S. application Ser. No.15/364,030, filed Nov. 29, 2016, entitled EFFICIENT SIGNALING SCHEME FORHIGH-SPEED ULTRA SHORT REACH INTERFACES, which claims priority to U.S.Provisional Application No. 62/314,237, filed Mar. 28, 2016, entitledEFFICIENT SIGNALING SCHEME FOR HIGH-SPEED VSR LINKS, and U.S.Provisional Application No. 62/341,871, filed May 26, 2016, entitledEFFICIENT SIGNALING SCHEME FOR HIGH-SPEED ULTRA SHORT REACH INTERFACES,all of which are incorporated herein by reference in their entirety.

TECHNICAL FIELD

The disclosure herein relates to communications systems, and morespecifically to high-speed multi-chip signaling systems and methods.

BACKGROUND

Integrated circuit chip designers continually integrate more and morefeatures and functions into single integrated circuit chips. Integratinginto such small scale often provides scale-related advantages andperformance, which is why SoCs (system on chip) approaches have been ofhigh interest in the past decade. However, very large chips with toomany functions integrated on them often lead to a yield and thus costdisadvantage. Because the defect density of a semiconductor fabricationprocess is generally fixed per unit area, the chip yield often dropsexponentially (not linearly) with an increase in area. One alternativeto integrating all functions and features into a single large chip is tospread the functions and features out among multiple smaller chips, andpackage the chips together into a single integrated circuit package.

While conventionally employing multiple chips into a single packageworks well for its intended applications, there are often instanceswhere the multiple chips need to communicate amongst themselves at veryhigh data rates. Enabling such high-throughput communication among anytwo or more chips in the same package (or module) in a power efficientand cost efficient manner would be highly desirable.

BRIEF DESCRIPTION OF THE DRAWINGS

Embodiments of the disclosure are illustrated by way of example, and notby way of limitation, in the figures of the accompanying drawings and inwhich like reference numerals refer to similar elements and in which:

FIG. 1 illustrates one embodiment of a multi-chip module (MCM) for aquad-PHY Ethernet transceiver circuit.

FIG. 2 illustrates one embodiment of a bidirectional single-endedsignaling link for use in the multi-chip module of FIG. 1.

FIG. 3 illustrates a further embodiment of two multi-chip modules fortwo dual-PHY Ethernet transceiver circuits.

FIG. 4 illustrates an additional embodiment of a quad multi-chip modulewith a dual XFI interface.

FIG. 5 illustrates one embodiment of a driver circuit for use with oneor more of the MCM embodiments described in FIGS. 1-4 and 6.

FIG. 6 illustrates an N-Tbps Switch ASIC with SerDes cores disposed on acommon multi-chip module.

DETAILED DESCRIPTION

Embodiments of apparatus and methods for efficient signaling for ultrashort reach (USR) links are disclosed. In one embodiment, a masterintegrated circuit (IC) chip is disclosed that includes transmitcircuitry and receiver circuitry. The transmit circuitry includes atiming signal generation circuit to generate a first timing signal, anda driver to transmit first data in response to the first timing signal.A timing signal path routes the first timing signal in a sourcesynchronous manner with the first data. The receiver circuitry includesa receiver to receive second data from a slave IC chip, and samplingcircuitry to sample the second data in response to a second timingsignal that is derived from the first timing signal.

In a further embodiment, a multi-chip module is disclosed that includesmultiple Ethernet ports, each port formed on a dedicated integratedcircuit (IC) chip and including Ethernet transceiver circuitry forming aline side of an Ethernet channel. The multi-chip module includes aserial interface end that is configured for connecting to less than allof the IC chips. Each chip includes an on-chip transfer interfaceoperable to transfer data to an adjacent IC chip. The IC chips areconfigured to transfer data between the multiple Ethernet ports and theserial interface. In this manner, multi-chip modules may be used in datatransfers between a defined number of Ethernet ports, and areduced-in-number set of serial links.

FIG. 1 illustrates one embodiment of a multi-chip module (MCM)architecture, generally designated 100. Multiple integrated circuit (IC)chips PHY 0, PHY 1, PHY 2 and PHY 3 are disposed on a package substrate110 to form an IC package. Each IC chip represents a high-speed Ethernettransceiver, often referred to as a “PHY.”

Further referring to FIG. 1, each PHY includes signal conditioningcircuitry PMA, such as crosstalk cancellers, echo cancellers, adaptivefilters, and so forth that may be employed consistent with high-speedEthernet standards, including for example 10GBASE-T and NBASE-T. The PMAforms one end of an Ethernet channel or port, such as at 102, forconnection to an Ethernet medium, such as twisted pair copper cable. Forone embodiment, each Ethernet channel transceives data at up to a 2.5Gbps data rate, for an aggregate data rate of 10 Gbps. The signalconditioning circuitry PMA couples to a physical coding sublayer PCSthat performs a variety of Ethernet-based coding functions.

Further referring to FIG. 1, each IC chip includes an off-chip datatransfer interface 112 that efficiently transfers and/or receives datafrom one or more adjacent IC chips for data aggregation purposes. Asexplained in further detail with respect to FIG. 2, each transferinterface includes plural bidirectional source synchronous links, suchas at 114, to route data and an accompanying timing signal, such as adouble-data rate (DDR) clock, from one chip to an adjacent chip. In somecircumstances, a given transfer interface may act as a repeater to passdata to a chip that originates from a non-adjacent chip. Using themiddle chips, such as PHY1 and PHY2, as signal repeaters eliminates theneed to route those signal through the package/module layers and underthe middle chips where routability is very limited and adding routinglayers is fairly costly. Ultra-sub-micron chips with very high routingdensity can easily provide many repeater channels at very low cost. Thetiming of a digital data bus that passes through a middle chip can beconserved to be the same as the source chip or alternativelyresynchronized to the middle chip clock domain before passing to thefollowing chip.

With continued reference to FIG. 1, each IC chip also includes a serialinterface port labeled as KR/PCS that is selectively enabled based onthe module configuration. One specific embodiment utilizes a USXGMIIport for each chip. For the embodiment of FIG. 1, only the serialinterface for PHY 1 has been enabled, at 116. Consequently, for thespecific configuration shown, all data transferred to and from the MDIlink end, which has the four Ethernet ports 102, is done so through theone enabled serial link port KR/PCS associated with PHY 1, at 116.

FIG. 2 illustrates one embodiment of a bidirectional signaling link,generally designated 200, for transferring and receiving data betweenadjacent transfer interface circuits, such as those identified in FIG. 1at 112. For purposes of clarity, a single-ended link is shown, but theprinciples described may apply equally to a differential link. For someembodiments, eight such links may be connected to a given transferinterface for each chip (four links to one chip, four links to another).One end of the link may be configured as a master integrated circuit(IC) chip 201 “MASTER”, while the other end may be configured as a slaveIC chip 205 “SLAVE.” The master IC chip generates and supplies a timingsignal such as a clock signal CK along a clock path 205 to synchronizethe transfer and receipt of data via the link in a source synchronousfashion.

As noted above, transmit and receive operations on the slave IC chip 203are timed by the timing signal generated by the master IC chip 201. Thisenables the slave IC chip to function without the need for it togenerate its own clock for transmit and receive operations, therebyreducing circuit complexity. The master and slave allocation can bedesigned to be programmable so the chip can operate properly indifferent multi-chip configurations. For one embodiment, the clocksignal is a double data rate (DDR) clock at a frequency of 625 MHZ. Theclock frequency is generated off of a 1.25 GHz source to ensure a 50%clock duty cycle. For very high signaling rates where the package tracelengths need to be treated like transmission lines, the bidirectionaltransceiver on either end of the link should provide a propertermination impedance to the package trace to eliminate or minimizesignal reflections. To reduce power, the package/module traces areconfigured with an appropriately high characteristic impedance.

Further referring to FIG. 2, the master end of the link will bedescribed in further detail, with the understanding that the slave endis formed similarly. Each end of the link includes a main driver 202 totransmit a data signal along a link 204. For one embodiment, the datatransfer rate may be set up to 1.25 Gbps, but other rates are possibledepending on the application. A replica driver 206 generates a replicadata signal for supplying to a summing circuit 208. The summing circuitalso receives a received data signal from receive path 210 that isreceived over the link 204. Since the link is simultaneouslybidirectional, transmit and receive signals may be superposed on eachother. The summing circuit 208 subtracts the transmit signal from thereceived signal so that the received data can be properly sampled by asampler 212.

The timing for the drivers 202 and 206, and the sampler 212 is based onthe master clock CK that is generated by a suitable clock source 214.The master clock is distributed to each of the drivers 202, 206, thesampler 212 and the slave IC chip 203 to achieve synchronization. Forone embodiment, a round trip propagation delay in the master clocksignal received from the slave IC chip may be compensated for byproviding a phase alignment circuit 216 (shown in phantom) at the inputof the sampler timing port. In one embodiment, the phase alignmentcircuit takes the form of a clock vernier. Other circuits may also beutilized for the phase alignment, such as a phase interpolator, aprogrammable delay line and so forth. The slave end of the link isformed similar to the master end, but utilizes the master clock signalfor synchronization purposes, thereby freeing the slave IC chip from theoverhead and complexity associated with the timing circuitry residing inthe master IC chip 201. The slave end may also benefit from phasealignment at its receiver to improve sampling timing margins.

In operation, the MCM 100 of FIG. 1 is configured with four Ethernetports 102 at the line end, and a single serial link port 116 oppositethe line end. From a data receive perspective at the line end, the MCMof FIG. 1 receives data from the four Ethernet ports PHY 0-PHY 3 at adata rate of 2.5 Gbps for each port, and directs the data and aggregatesit for transfer along the serial port 116 enabled for PHY1, at a 10 Gbpsdata rate.

Further referring to FIG. 1, the 2.5 Gbps data received by PHY 0 istransferred along two of the single-ended links 114 provided by thetransfer interface (shown in FIG. 2) to the transfer interface of PHY 1,with each link operating at, for example, 1.25 Gbps. A link alsoprovides a 625 MHz DDR clock for source synchronous timingsynchronization. The transfer interface for PHY 1 includes fouradditional I/O ports that connect to four more links that are connectedto PHY 2. Two of the links transfer the 2.5 Gbps data received by theEthernet port of PHY 2, while the other two links provide 2.5 Gbps datatransferred from PHY 3 to PHY 2 (along two transfer interface linksbetween PHY 2 and PHY 3). PHY 2 thus acts as a repeater for the databeing transferred from PHY 3. When aggregated at PHY 1, the data may beserialized in an acceptable manner to achieve a 10 Gbps data transferrate at the serial interface KR/PCS, at 116.

FIG. 3 illustrates an embodiment of two dual port multi-chip modules(MCM), 302 and 304. Each MCM includes a pair of Ethernet transceiverchips disposed on a package substrate, such as PHY 0, PHY 1 and PHY 2,PHY 3. Each chip includes an Ethernet port 306 for connecting to anEthernet cable and transceiving data at a rate of, for example, 5 Gbps.Respective transfer interface circuits 308 are disposed on each chip totransfer data between the pair of chips for each module. Serialinterface circuitry 310 on each chip is selectively enabled such that,for example, only one serial interface port is utilized for each MCM 302and 304 to transfer data at 10 Gbps. The transfer interface 308 allowsfor an aggregation/disaggregation of data between the two Ethernet portsand a single serial link, similar to the 4:1 aggregation ratio describedwith the MCM architecture of FIG. 1. Needless to say, the four ports inFIG. 3 can all be bundled in a single multi-chip module (on the samesubstrate), while all connections stay the same as shown.

One embodiment of a quad MCM that implements a dual SerDes interface isshown in FIG. 4, generally designated 400. The MCM includes fourEthernet transceiver chips PHY0, PHY1, PHY2, and PHY3 that are mountedon a common package substrate (not shown). The chips each include anEthernet port, such as at 402, and a serial port, such as at 404. Forone embodiment, the Ethernet ports each transceive data at 5 Gbps. Asmore fully explained below, less than all of the serial ports areenabled. To steer data and aggregate data for fewer (but faster) serialports, each chip includes one clock pin, such as at 406, and twobi-directional single-ended data pins, such as at 408 and 410. For oneembodiment, each data pin transmits and receives data at 2.5 Gbps, whilethe clock pin carries a double-data rate (DDR) clock at a frequency of1.25 GHz. A slave PHY, such as PHY0, uses the clock associated with amaster PHY, such as PHY1, to receive data from the master PHY andtransmit data back to the master PHY. For one embodiment, the master andslave designations are hard-coded. Aggregated data may be transferredserially over enabled serial ports 404 and 405 at, for example, 10 Gbps.

For some embodiments, it may be desirable to limit power consumption bytaking into consideration the optimal value of a termination impedanceassociated with each link driver. FIG. 5 illustrates one embodiment of abi-directional signaling scheme for a driver circuit 500 using avoltage-mode driver. Depending on the choice of a characteristicimpedance R=Zo, the circuit may be configured to exhibit high impedancewith low-power dissipation, or low-impedance with high powerdissipation. The driver circuit 500 includes a voltage modedigital-to-analog converter (DAC) 502 with a digital data input 504 andan analog output 506 that generates an output voltage 2*V_(TX). Thedriver output 506 couples to a transmission line 508, and includes atermination impedance R that substantially matches a characteristicimpedance Z₀ of the transmission line.

Further referring to FIG. 5, the output driver node 506 also couples toan impedance network, or hybrid circuit 507, that includes a hybridimpedance R_(Hr) in series with a replica termination impedance R_(Tr).The resulting voltage V_(TX) at the node 512 connecting R_(Hr) andR_(Tr) is fed to a gain stage k, then to an input 514 of a receiver 516.For some embodiments, the gain stage k may include circuitry inside thereceiver 516. Alternatively, instead of the gain stage k, a gain stage1/k may be placed between receiver input 518 and line 510. A secondinput 518 of the receiver 516 couples to the transmission line 508 toreceive a summed voltage of a receive data voltage V_(RX) and thetransmit data voltage V_(TX). The common voltage components at thereceiver cancel out, thus leaving a resulting receive voltage of V_(RX).

With continued reference to FIG. 5, for ultra-short reach (USR) linksthat have minimal or no attenuation due to channel high-frequencylosses, the value of the line and termination resistance can be madelarger than a typical 100 ohm (differential) or 50 ohm (single-ended)characteristic impedances. A larger value for the termination impedance,while resulting in potential losses at higher frequencies, neverthelessenables additional power reduction. Moreover, the higher terminationresistance means smaller current pulses for the same voltage amplitude,and thus smaller driver induced noise into the supply network.

Another method to reduce power further, in parallel with increasing theline & termination resistance as described above, is to minimize thepower in the hybrid (transmit replica) path. The lowest power in thehybrid path may be realized by the relationship:Hybrid topology A) R _(Tr)=Open circuit (infinite impedance) with“k”=0.5In the above scenario, the transmit main path and hybrid path will notbe the best match across frequency and thus the cancellation may notoptimal. On the other hand, the optimal hybrid cancellation acrossfrequency may be realized by the following relationship:Hybrid topology B) R _(Hr) =R _(Tr) =Z ₀ with “k”=1.0In many ultra-short reach applications (such as in MCM packages), thereceived signal-to-noise ratio (SNR) is high, such that a reduction inpower can be carried out successfully using hybrid topology A as well ashigher termination & line impedance without impacting the bit errorrate.

FIG. 6 illustrates a further embodiment of a multi-chip module (MCM),generally designated 600. The MCM includes a substrate 602 that mountsan application specific integrated circuit (ASIC) 604 that, for oneembodiment, is fabricated and programmed to carry out the function of anetwork switch capable of handling data traffic at N-Tbps data rates.The MCM 600 includes multiple IC chips in the form ofserializer-deserializer (SerDes) cores 606 disposed on the substrate602. For one specific embodiment, each SerDes core 606 couples to theASIC 604 via source-synchronous bidirectional interfaces that employmultiple groups 608 of serial links in the form of input/output (I/O)circuits. In one embodiment, each I/O transmits and receives up toapproximately 28 Gbps (NRZ data) or approximately 56 Gbps (PAM4 data).Each group of links (such as four differential data links) is associatedwith a source-synchronous DDR clock link, such as at 610, capable ofrunning at, for example, 14 GHz. For some embodiments, the clock signalstransferred along the clock lines may be sourced from the SerDes cores606 (acting as a master IC chip for timing synchronization purposes) andpassed to the ASIC 604 (acting as a slave IC chip for timingsynchronization purposes) to receive and transmit data. For suchembodiments, the phase alignment circuit, such as the clock vernier 216(FIG. 2), may also be employed for optimal receiver sampling in theSerDes cores. In other embodiments, however, the clock vernier may beeliminated by employing a bidirectional clocking architecture such thatboth sides receive the clock whose phase is aligned with the receivedata phase.

In some embodiments, the trace lengths between the SerDes cores 606 andthe ASIC 604 (less than 1 inch) may be configured to provide properround trip phase relationship between receive and transmit data for anysymbol time. For one embodiment, respective phase alignments betweentransmit and receive data may be optimally offset such that signaltransitions are non-aligned, resulting in a more optimal eye opening forreceiver sampling purposes. One embodiment for a circuit to carry thisout is disclosed in application Ser. 62/317,493, titled “Dual-DuplexLink With Independent Transmit and Receive Phase Adjustment”, filed Apr.1, 2016, assigned to the assignee of the instant application, andincorporated by reference in its entirety.

With continued reference to FIG. 6, each link in the groups of linksmaking up the interface may include driver circuits at each end, similarto the driver circuit described with respect to FIG. 5. For one specificembodiment, each pin includes a driver and hybrid circuit with areceiver sampler (three samplers if PAM 4 is utilized), a clock vernier(only for very high baud rates, such as greater than 10GBaud),serial-to-parallel conversion circuits, and an elastic buffer in theASIC to synchronize data to the SerDes clock domain and vice versa. Forsome embodiments, the termination impedance may be optimized along withthe baud rate and signal and power integrity requirements to achieveapproximately 1 mW/Gbps or less. For embodiments that may utilize PAM4symbols, relatively straightforward equalization such as transmitpre-emphasis may be employed as a design tradeoff for adjusting thetermination impedance to higher values.

The MCM 600 of FIG. 6 provides minimal overhead and complexity whilesimultaneously providing very high data rates for a network switchenvironment. The source-synchronous clocks eliminate the need for ultralow-jitter clock generation phase-locked loops (PLL), as well as complexclock and data recovery (CDR) circuits. In the master side, such as theSerDes chips in FIG. 6, a relaxed clock generation source as well as asimple phase alignment circuitry instead of a complex CDR can deliverthe required performance. On the slave side, such as the ASIC chip inFIG. 6, all analog circuitries such as a clock source, and a phasealignment block can be completely eliminated. Further, the short traceseliminate the need for complex equalization.

When received within a computer system via one or more computer-readablemedia, such data and/or instruction-based expressions of the abovedescribed circuits may be processed by a processing entity (e.g., one ormore processors) within the computer system in conjunction withexecution of one or more other computer programs including, withoutlimitation, net-list generation programs, place and route programs andthe like, to generate a representation or image of a physicalmanifestation of such circuits. Such representation or image maythereafter be used in device fabrication, for example, by enablinggeneration of one or more masks that are used to form various componentsof the circuits in a device fabrication process.

In the foregoing description and in the accompanying drawings, specificterminology and drawing symbols have been set forth to provide athorough understanding of the present invention. In some instances, theterminology and symbols may imply specific details that are not requiredto practice the invention. For example, any of the specific numbers ofbits, signal path widths, signaling or operating frequencies, componentcircuits or devices and the like may be different from those describedabove in alternative embodiments. Also, the interconnection betweencircuit elements or circuit blocks shown or described as multi-conductorsignal links may alternatively be single-conductor signal links, andsingle conductor signal links may alternatively be multi-conductorsignal links. Signals and signaling paths shown or described as beingsingle-ended may also be differential, and vice-versa. Similarly,signals described or depicted as having active-high or active-low logiclevels may have opposite logic levels in alternative embodiments.Component circuitry within integrated circuit devices may be implementedusing metal oxide semiconductor (MOS) technology, bipolar technology orany other technology in which logical and analog circuits may beimplemented. With respect to terminology, a signal is said to be“asserted” when the signal is driven to a low or high logic state (orcharged to a high logic state or discharged to a low logic state) toindicate a particular condition. Conversely, a signal is said to be“deasserted” to indicate that the signal is driven (or charged ordischarged) to a state other than the asserted state (including a highor low logic state, or the floating state that may occur when the signaldriving circuit is transitioned to a high impedance condition, such asan open drain or open collector condition). A signal driving circuit issaid to “output” a signal to a signal receiving circuit when the signaldriving circuit asserts (or deasserts, if explicitly stated or indicatedby context) the signal on a signal line coupled between the signaldriving and signal receiving circuits. A signal line is said to be“activated” when a signal is asserted on the signal line, and“deactivated” when the signal is deasserted. Additionally, the prefixsymbol “I” attached to signal names indicates that the signal is anactive low signal (i.e., the asserted state is a logic low state). Aline over a signal name (e.g., ‘<signal name>’) is also used to indicatean active low signal. The term “coupled” is used herein to express adirect connection as well as a connection through one or moreintervening circuits or structures. Integrated circuit device“programming” may include, for example and without limitation, loading acontrol value into a register or other storage circuit within the devicein response to a host instruction and thus controlling an operationalaspect of the device, establishing a device configuration or controllingan operational aspect of the device through a one-time programmingoperation (e.g., blowing fuses within a configuration circuit duringdevice production), and/or connecting one or more selected pins or othercontact structures of the device to reference voltage lines (alsoreferred to as strapping) to establish a particular device configurationor operation aspect of the device. The term “exemplary” is used toexpress an example, not a preference or requirement.

While the invention has been described with reference to specificembodiments thereof, it will be evident that various modifications andchanges may be made thereto without departing from the broader spiritand scope of the invention. For example, features or aspects of any ofthe embodiments may be applied, at least where practicable, incombination with any other of the embodiments or in place of counterpartfeatures or aspects thereof. Accordingly, the specification and drawingsare to be regarded in an illustrative rather than a restrictive sense.

We claim:
 1. An integrated circuit (IC) chip, comprising: transceivercircuitry, the transceiver circuitry including a differential transmitcircuit including a first transmit path for transmitting first data of afirst polarity to a transmission line, a second transmit path forgenerating replica first data having a second polarity opposite thefirst polarity; and a hybrid circuit including a first input pathcoupled to the second transmit path, a second input path coupled to thetransmission line for receiving a first summed signal including thefirst data and second data, the second data received from thetransmission line simultaneous with transmission of the first data alongthe transmission line, and an output circuit to generate an outputrepresenting a summation of the replica first data and the first summedsignal.
 2. The IC chip of claim 1, wherein the first transmit pathincludes an impedance for driving the first data onto the transmissionline.
 3. The IC chip of claim 1, wherein the first input path includes aresistor divider network.
 4. The IC chip of claim 3, wherein theresistor divider network includes: a hybrid resistor in series with areplica termination resistor.
 5. The IC chip of claim 4, wherein: thehybrid resistor exhibits a first resistance that substantially matches asecond resistance exhibited by the replica termination resistor.
 6. TheIC chip of claim 4, wherein: the replica termination resistor exhibitsan infinite resistance.
 7. The IC chip of claim 3, wherein: the resistordivider network is selectively tied to a fixed reference voltage.
 8. TheIC chip of claim 1, further comprising: receiver circuitry having areceiver input to receive the output from the output circuit.
 9. ASerDes transceiver circuit, comprising: a first simultaneousbidirectional transceiver for coupling to a first signaling link; asecond simultaneous bidirectional transceiver for coupling to a secondsignaling link, the first and second simultaneous bidirectionaltransceivers forming a dual-duplex configuration; and wherein each ofthe first and second simultaneous bidirectional transceivers includes adifferential transmit circuit including a first transmit path fortransmitting first data of a first polarity to a transmission line, asecond transmit path for generating replica first data having a secondpolarity opposite the first polarity; and a hybrid circuit including afirst input path coupled to the second transmit path, a second inputpath coupled to the transmission line for receiving a first summedsignal including the first data and second data, the second datareceived from the transmission line simultaneous with transmission ofthe first data along the transmission line, and an output circuit togenerate an output representing a summation of the replica first dataand the first summed signal.
 10. The SerDes transceiver circuit of claim9, wherein the first transmit path includes an impedance for driving thefirst data onto the transmission line.
 11. The SerDes transceivercircuit of claim 9, wherein the first input path includes a resistordivider network.
 12. The SerDes transceiver circuit of claim 11, whereinthe resistor divider network includes: a hybrid resistor in series witha replica termination resistor.
 13. The SerDes transceiver circuit ofclaim 12, wherein: the hybrid resistor exhibits a first resistance thatsubstantially matches a second resistance exhibited by the replicatermination resistor.
 14. The SerDes transceiver circuit of claim 12,wherein: the replica termination resistor exhibits an infiniteresistance.
 15. The SerDes transceiver circuit of claim 11, wherein: theresistor divider network is selectively tied to a fixed referencevoltage.
 16. The SerDes transceiver circuit of claim 9, furthercomprising: receiver circuitry having a receiver input to receive theoutput from the output circuitry.
 17. A method of operation in a SerDesintegrated circuit (IC) chip, comprising: transmitting first data of afirst polarity along a first transmit path to a transmission line,generating replica first data having a second polarity opposite thefirst polarity; and receiving second data from the transmission linesimultaneously with transmitting the first data, the receiving includingreceiving a first summed signal including the first data and the seconddata, and generating an output representing a summation of the replicafirst data and the first summed signal.